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| Order this document by MC34261/D Power Factor Controllers The MC34261/MC33261 are active power factor controllers specifically designed for use as a preconverter in electronic ballast and in off-line power converter applications. These integrated circuits feature an internal startup timer, a one quadrant multiplier for near unity power factor, zero current detector to ensure critical conduction operation, high gain error amplifier, trimmed internal bandgap reference, current sensing comparator, and a totem pole output ideally suited for driving a power MOSFET. Also included are protective features consisting of input undervoltage lockout with hysteresis, cycle-by-cycle current limiting, and a latch for single pulse metering. These devices are available in dual-in-line and surface mount plastic packages. * Internal Startup Timer MC34261 MC33261 POWER FACTOR CONTROLLERS SEMICONDUCTOR TECHNICAL DATA * * * * * * * * One Quadrant Multiplier Zero Current Detector Trimmed 2% Internal Bandgap Reference Totem Pole Output Undervoltage Lockout with Hysteresis Low Startup and Operating Current Pinout Equivalent to the SG3561 Functional Equivalent to the TDA4817 8 1 8 1 P SUFFIX PLASTIC PACKAGE CASE 626 D SUFFIX PLASTIC PACKAGE CASE 751 (SO-8) PIN CONNECTIONS Simplified Block Diagram Voltage Feedback Input Compensation Multiplier Input Current Sense Input 1 2 3 4 (Top View) 8 VCC 7 Drive Output 6 Gnd 5 Zero Current Detect Input Zero Current Detector 5 Zero Current Detect Input 2.5V Reference Undervoltage Lockout VCC 8 Drive Output Multiplier, Latch, PWM, Timer, & Logic 7 Current Sense Input 4 ORDERING INFORMATION Device Voltage Feedback 1 Input Compensation 2 MC34261D MC34261P MC33261D MC33261P Operating Temperature Range TA = 0 to +70C TA = - 40 to +85C Package SO-8 Plastic DIP SO-8 Plastic DIP Rev 1 Error Amp Multiplier Input 3 Gnd 6 Multiplier Vref (c) Motorola, Inc. 1996 MOTOROLA ANALOG IC DEVICE DATA 1 MC34261 MC33261 MAXIMUM RATINGS Rating Total Power Supply and Zener Current Output Current, Source or Sink (Note 1) Current Sense, Multiplier, and Voltage Feedback Inputs Zero Current Detect Input High State Forward Current Low State Reverse Current Power Dissipation and Thermal Characteristics P Suffix, Plastic Package Case 626 Maximum Power Dissipation @ TA = 70C Thermal Resistance, Junction-to-Air D Suffix, Plastic Package Case 626 Maximum Power Dissipation @ TA = 70C Thermal Resistance, Junction-to-Air Operating Junction Temperature Operating Ambient Temperature (Note 3) MC34261 MC33261 Storage Temperature Symbol (ICC + IZ) IO Vin Iin 50 -10 Value 30 500 -1.0 to 10 Unit mA mA V mA PD RJA PD RJA TJ TA 800 100 450 178 +150 0 to +70 -40 to +85 mW C/W mW C/W C C Tstg -55 to +150 C ELECTRICAL CHARACTERISTICS (VCC = 12 V, for typical values TA = 25C, for min/max values TA is the operating ambient temperature range that applies [Note 3], unless otherwise noted.) Characteristic ERROR AMPLIFIER Voltage Feedback Input Threshold TA = 25C TA = Tlow to Thigh (VCC = 12 V to 28 V) Line Regulation (VCC = 12 V to 28 V, TA = 25C) Input Bias Current (VFB = 0 V) Open Loop Voltage Gain Gain Bandwidth Product (TA = 25C) Output Source Current (VO = 4.0 V, VFB = 2.3 V) Output Voltage Swing High State (ISource = 0.2 mA, VFB = 2.3 V) Low State (ISink = 0.4 mA, VFB = 2.7 V) MULTIPLIER Dynamic Input Voltage Range Multiplier Input (Pin 3) Compensation (Pin 2) Input Bias Current (VFB = 0 V) Multiplier Gain (VPin 3 = 0.5 V, VPin 2 = VFB + 1.0 V) (Note 2) ZERO CURRENT DETECTOR Input Threshold Voltage (Vin Increasing) Hysteresis (Vin Decreasing) Input Clamp Voltage High State (IDET = 3.0 mA) Low State (IDET = -3.0 mA) NOTES: 1. Maximum package power dissipation limits must be observed. Pin 4 Threshold Voltage 2. K = VPin 3(VPin 2 - VFB) 3. Tlow = -40C for MC34261 Thigh = +70C for MC34261 3. Tlow = -40C for MC33261 Thigh = +85C for MC33261 Symbol Min Typ Max Unit VFB 2.465 2.44 Regline IIB AVOL GBW ISource VOH VOL - - 65 0.7 0.25 5.0 - 2.5 1.0 -0.3 85 1.0 0.5 5.7 2.1 2.535 2.54 10 -1.0 - - 0.75 - 2.44 V mV A dB MHz mA V V VPin 3 VPin 2 IIB K 0 to 2.5 VFB to (VFB + 1.0) - 0.4 0 to 3.5 VFB to (VFB + 1.5) -0.3 0.62 - - -1.0 0.8 A 1/V Vth VH VIH VIL 1.3 40 6.1 0.3 1.6 110 6.7 0.7 1.8 200 - 1.0 V mV V 2 MOTOROLA ANALOG IC DEVICE DATA MC34261 MC33261 ELECTRICAL CHARACTERISTICS (VCC = 12 V, for typical values TA = 25C, for min/max values TA is the operating ambient temperature range that applies [Note 3], unless otherwise noted.) Characteristic CURRENT SENSE COMPARATOR Input Bias Current (VPin 4 = 0 V) Input Offset Voltage (VPin 2 = 1.1 V, VPin 3 = 0 V) Delay to Output DRIVE OUTPUT Output Voltage (VCC = 12 V) Low State (ISink = 20 mA) Low State (ISink = 200 mA) High State (ISource = 20 mA) High State (ISource = 200 mA) Output Voltage (VCC = 30 V) High State (ISource = 20 mA, CL = 15 pF) Output Voltage Rise Time (CL = 1.0 nF) Output Voltage Fall Time (CL = 1.0 nF) Output Voltage with UVLO Activated (VCC = 7.0 V, ISink = 1.0 mA) RESTART TIMER Restart Time Delay UNDERVOLTAGE LOCKOUT Startup Threshold (VCC Increasing) Minimum Operating Voltage After Turn-On (VCC Decreasing) Hysteresis TOTAL DEVICE Power Supply Current Startup (VCC = 7.0 V) Operating Dynamic Operating (50 kHz, CL = 1.0 nF) Power Supply Zener Voltage NOTES: 1. Maximum package power dissipation limits must be observed. Pin 4 Threshold Voltage 2. K = VPin 3(VPin 2 - VFB) 3. Tlow = -40C for MC34261 3. Tlow = -40C for MC33261 Thigh = +70C for MC34261 Thigh = +85C for MC33261 Symbol Min Typ Max Unit A mV ns IIB VIO tPHL (in/out) - - - -0.5 3.5 200 -2.0 15 400 V VOL VOH VO(max) 14 tr tf VOH(UVLO) - - - 16 50 50 0.2 18 120 120 0.8 ns ns V s - 1.8 9.8 7.8 0.3 2.4 10.3 8.3 0.8 3.3 - 8.8 V tDLY 150 400 - Vth VShutdown VH 9.2 7.0 1.75 10.0 8.0 2.0 10.8 9.0 2.5 V V V ICC - - - VZ 30 0.3 7.1 9.0 36 0.5 12 20 - mA V V CS , CURRENT SENSE THRESHOLD VOLTAGE (V) 3.0 2.5 2.0 1.5 1.0 0.5 0 See Figure 2 -0.5 -0.5 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 V CS , CURRENT SENSE THRESHOLD VOLTAGE (V) Figure 1. Current Sense Input Threshold versus Multiplier Input Figure 2. Current Sense Input Threshold versus Multiplier Input 0.16 0.14 0.12 0.10 0.08 0.06 0.04 0.02 0 -0.02 -0.12 -0.08 -0.04 0 0.04 0.08 0.12 VM, MULTIPLIER INPUT VOLTAGE (V) VM, MULTIPLIER INPUT VOLTAGE (V) MOTOROLA ANALOG IC DEVICE DATA 3 MC34261 MC33261 VFB , VOLTAGE FEEDBACK THRESHOLD CHANGE (mV) Figure 3. Voltage Feedback Input Threshold Change versus Temperature 100 VCC = 12 V Pins 1 to 2 0 A VOL, OPEN LOOP VOLTAGE GAIN (dB) 80 60 40 20 0 Figure 4. Error Amp Open Loop Gain and Phase versus Frequency 0 VCC = 12 V VO = 3.0 V to 3.5 V RL = 100 k TA = 25C 30 60 90 Phase 120 150 180 10 M , EXCESS PHASE ( C) 200 mV/DIV 1.0 s/DIV +4.0 Gain -4.0 -8.0 -12 -16 -55 -25 0 25 50 75 100 125 -20 10 100 1.0 k 10 k 100 k 1.0 M TA, AMBIENT TEMPERATURE (C) f, FREQUENCY (Hz) Figure 5. Error Amp Small Signal Transient Response 2.55 V VCC = 12 V AV = -1.0 TA = 25C 3.0 V Figure 6. Error Amp Large Signal Transient Response VCC = 12 V AV = -1.0 TA = 25C 20 mV/DIV 0.5 s/DIV 2.5 V 2.5 V 2.45 V 2.0 V Figure 7. Error Amp Output Saturation versus Sink Current 5.0 Vsat , OUTPUT SATURATION VOLTAGE (V) t DLY , RESTART TIME DELAY ( s) VCC = 12 V VFB = 2.7 V 4.0 TA = 25C 3.0 525 Figure 8. Restart Time Delay versus Temperature 475 425 VCC = 12 V 2.0 375 1.0 325 0 0 0.5 1.0 1.5 ISink, OUTPUT SINK CURRENT (mA) 2.0 275 -55 -25 0 25 50 75 TA, AMBIENT TEMPERATURE (C) 100 125 4 MOTOROLA ANALOG IC DEVICE DATA MC34261 MC33261 Figure 9. Zero Current Detector Input Threshold Voltage Change versus Temperature V th , THRESHOLD VOLTAGE CHANGE (mV) 40 Vsat , OUTPUT SATURATION VOLTAGE (V) 0 -2.0 -4.0 -6.0 4.0 2.0 0 Source Saturation (Load to Ground) Figure 10. Output Saturation Voltage versus Load Current VCC VCC = 12 V 80 s Pulsed Load 120 Hz Rate 20 VCC = 12 V 0 Upper Threshold (Vin Increasing) -20 Lower Threshold (Vin Decreasing) -40 -55 -25 0 25 50 75 TA, AMBIENT TEMPERATURE (C) 100 125 Sink Saturation (Load to VCC) Gnd 0 80 160 240 IO, OUTPUT LOAD CURRENT (mA) 320 90 % I CC , SUPPLY CURRENT 10 % 100 ns/DIV 100 ns/DIV Figure 13. Supply Current versus Supply Voltage 16 12 11 12 VCC , SUPPLY VOLTAGE (V) 10 9.0 8.0 7.0 6.0 -55 Figure 14. Undervoltage Lockout Thresholds versus Temperature I CC , SUPPLY CURRENT (mA) Startup Threshold (VCC Increasing) 8.0 VFB = 0 V Current Sense = 0 V Multiplier = 0 V CL = 1.0 nF f = 50 kHz TA = 25C 0 10 20 VCC, SUPPLY VOLTAGE (V) 30 40 4.0 Minimum Operating Threshold (VCC Decreasing) 0 -25 0 25 50 75 TA, AMBIENT TEMPERATURE (C) 100 125 MOTOROLA ANALOG IC DEVICE DATA 5 100 mA/DIV 5.0 V/DIV VCC = 12 V CL = 1.0 nF TA = 25C VO , OUTPUT VOLTAGE Figure 11. Drive Output Waveform Figure 12. Drive Output Cross Conduction VCC = 12 V CL = 15 pF TA = 25C MC34261 MC33261 FUNCTIONAL DESCRIPTION Introduction Most electronic ballasts and switching power supplies use a bridge rectifier and a filter capacitor to derive raw dc voltage from the utility ac line. This simple rectifying circuit draws power from the line when the instantaneous ac voltage exceeds the capacitor's voltage. This occurs near the line voltage peak and results in a high charge current spike. Since power is only taken near the line voltage peaks, the resulting spikes of current are extremely nonsinusoidal with a high content of harmonics. This results in a poor power factor condition where the apparent input power is much higher than the real power. The MC34261, MC33261 are high performance, critical conduction, current mode power factor controllers specifically designed for use in off-line active preconverters. These devices provide the necessary features required to significantly enhance poor power factor loads by keeping the ac line current sinusoidal and in phase with the line voltage. With proper control of the preconverter, almost any complex load can be made to appear resistive to the ac line, thus significantly reducing the harmonic current content. Operating Description The MC34261, MC33261 contains many of the building blocks and protection features that are employed in modern high performance current mode power supply controllers. There are, however, two areas where there is a major difference when compared to popular devices such as the UC3842 series. Referring to the block diagram in Figure 15, note that a multiplier has been added to the current sense loop and that this device does not contain an oscillator. A description of each of the functional blocks is given below. Error Amplifier A fully compensated Error Amplifier with access to the inverting input and output is provided. It features a typical dc voltage gain of 85 dB, and a unity gain bandwidth of 1.0 MHz with 58 of phase margin (Figure 4). The noninverting input is internally biased at 2.5 V 2.0% and is not pinned out. The output voltage of the power factor converter is typically divided down and monitored by the inverting input. The maximum input bias current is -1.0 A which can cause an output voltage error that is equal to the product of the input bias current and the value of the upper divider resistor R2. The Error Amp Output is internally connected to the Multiplier and is pinned out (Pin 2) for external loop compensation. Typically, the bandwidth is set below 20 Hz, so that the Error Amp output voltage is relatively constant over a given ac line cycle. The output stage consists of a 500 A current source pull-up with a Darlington transistor pull-down. It is capable of swinging from 2.1 V to 5.7 V, assuring that the Multiplier can be driven over its entire dynamic range. Multiplier A single quadrant, two input multiplier is the critical element that enables this device to control power factor. The ac haversines are monitored at Pin 3 with respect to ground while the Error Amp output at Pin 2 is monitored with respect to the Voltage Feedback Input threshold. A graph of the Multiplier transfer curve is shown in Figure 1. Note that both inputs are extremely linear over a wide dynamic range, 0 V to 3.2 V for the Multiplier input (Pin 3), and 2.5 V to 4.0 V for the Error Amp output (Pin 2). The Multiplier output controls the Current Sense Comparator threshold (Pin 4) as the ac voltage traverses sinusoidally from zero to peak line. This has the effect of forcing the MOSFET peak current to track the input line voltage, thus making the preconverter load appear to be resistive. Pin 4 Threshold 0.62(VPin 2 - VFB)VPin 3 Zero Current Detector The MC34261 operates as a critical conduction current mode controller, whereby output switch conduction is initiated by the Zero Current Detector and terminated when the peak inductor current reaches the threshold level established by the Multiplier output. The Zero Current Detector initiates the next on-time by setting the RS Latch at the instant the inductor current reaches zero. This critical conduction mode of operation has two significant benefits. First, since the MOSFET cannot turn on until the inductor current reaches zero, the output rectifier's reverse recovery time becomes less critical allowing the use of an inexpensive rectifier. Second, since there are no deadtime gaps between cycles, the ac line current is continuous thus limiting the peak switch to twice the average input current. The Zero Current Detector indirectly senses the inductor current by monitoring when the auxiliary winding voltage falls below 1.6 V. To prevent false tripping, 110 mV of hysteresis is provided. The Zero Current Detector input is internally protected by two clamps. The upper 6.7 V clamp prevents input overvoltage breakdown while the lower 0.7 V clamp prevents substrate injection. Device destruction can result if this input is shorted to ground. An external resistor must be used in series with the auxiliary winding to limit the current through the clamps. Current Sense Comparator and RS Latch The Current Sense Comparator RS Latch configuration ensures that only a single pulse appears at the Drive Output during a given cycle. The inductor current is converted to a voltage by inserting a ground referenced sense resistor R9 in series with the source of output switch Q1. This voltage is monitored by the Current Sense Input and compared to the Multiplier output voltage. The peak inductor current is controlled by the threshold voltage of Pin 4 where: Pin 4 Threshold R9 Ipk = With the component values shown in Figure 16, the Current Sense Comparator threshold, at the peak of the haversine varies from 1.1 V at 90 Vac to 100 mV at 268 Vac. The Current Sense Input to Drive Output propagation delay is typically 200 ns. 6 MOTOROLA ANALOG IC DEVICE DATA MC34261 MC33261 Timer A watchdog timer function was added to the IC to eliminate the need for an external oscillator when used in stand alone applications. The Timer provides a means to automatically start or restart the preconverter if the Drive Output has been off for more than 400 s after the inductor current reaches zero. Undervoltage Lockout An Undervoltage Lockout comparator guarantees that the IC is fully functional before enabling the output stage. The positive power supply terminal (VCC) is monitored by the UVLO comparator with the upper threshold set at 10 V and the lower threshold at 8.0 V (Figure 14). In the standby mode, with VCC at 7.0 V, the required supply current is less than 0.5 mA (Figure 13). This hysteresis and low startup current allow the implementation of efficient bootstrap startup techniques, making these devices ideally suited for wide input range off line preconverter applications. An internal 36 V clamp has been added from VCC to ground to protect the IC and capacitor C5 from an overvoltage condition. This feature is desirable if external circuitry is used to delay the startup of the preconverter. Output The MC34261/MC33261 contain a single totem pole output stage specifically designed for direct drive of power MOSFETs. The Drive Output is capable of up to 500 mA peak current with a typical rise and fall time of 50 ns with a 1.0 nF load. Additional internal circuitry has been added to keep the Drive Output in a sinking mode whenever the Undervoltage Lockout is active. This characteristic eliminates the need for an external gate pull-down resistor. The totem pole output has been optimized to minimize cross conduction current during high speed operation. The addition of two 10 resistors, one in series with the source output transistor and one in series with the sink output transistor, reduces the cross conduction current, as shown in Figure 12. A 16 V clamp has been incorporated into the output stage to limit the high state VOH. This prevents rupture of the MOSFET gate when VCC exceeds 20 V. Table 1. Design Equations Notes Calculate the maximum required output power. Calculated at the minimum required ac line for regulation. Let the efficiency n = 0.95. Let the switching cycle t = 20 s. Inductance 2t L= Calculation Required Converter Output Power Peak Inductor Current Formula PO = VO IO IL(pk) = 2 2 PO Vac(LL) VO - Vac Vac2 2 VO Vac(LL) IL(pk) In theory the on-time ton is constant. In practice ton tends to increase at the ac line zero crossings due to the charge on capacitor C6. The off-time toff is greatest at peak ac line and approaches zero at the ac line zero crossings. Theta () represents the angle of the ac line voltage. The minimum switching frequency occurs at peak ac line and increases as toff decreases. Set the current sense threshold VCS to 1.0 V for universal input (85 Vac to 265 Vac) operation and to 0.5 V for fixed input (92 Vac to 138 Vac, or 184 to 276 Vac) operation. Set the multiplier input voltage VM to 3.0 V at high line. Empirically adjust VM for the lowest distortion over the ac line range while guaranteeing startup at minimum line. The IIB R1 error term can be minimized with a divider current in excess of 100 A. The bandwidth is typically set to 20 Hz for minimum output ripple over the ac line haversine. Switch On-Time ton = 2 PO L Vac2 ton VO 2 Vac Sin Switching Frequency f= 1 ton + toff VCS IL(pk) Vac R7 R3 Converter Output Voltage VO = Vref 2 +1 -1 Switch Off-Time toff = Peak Switch Current R9 = Multiplier Input Voltage VM = R2 +1 R1 1 - IIB R2 BW = Error Amplifier Bandwidth 2 R1 R2 R1 + R 2 C1 The following converter characteristics must be chosen: Vac - AC RMS line voltage VO - Desired output voltage IO - Desired output current Vac(LL) - AC RMS low line voltage MOTOROLA ANALOG IC DEVICE DATA 7 MC34261 MC33261 Figure 15. 80 W Power Factor Controller 1 D2 92 to RFI 138 Vac Filter D4 Zero Current Detector 1.2V + + + 36V 6.7V 5 C6 100k R8 8 + 1N4934 D6 100 C5 22k R5 T D1 D3 1.6V UVLO 2.5V Reference + 10V MUR130 D5 + 7 10 R6 MTP 8N50E Q1 VO 100 C4 230V/0.35A Timer R Delay RS Latch 2.2M R7 16V Drive Output 10 10 Current Sense Comparator Multiplier 3 6 4 + Error Amp Vref 0.5mA 1 2 0.68 C1 330 R4 1.0nF C3 0.1 R9 1.0M R2 0.01 C2 7.5k R3 11k R1 Power Factor Controller Test Data AC Line Input Current Harmonic Distortion (%) Vrms 90 100 110 120 130 138 Pin 85.6 85.1 84.8 84.5 84.2 84.1 PF -0.998 -0.997 -0.997 -0.997 -0.996 -0.995 THD 2.4 5.0 5.3 5.8 6.6 7.2 2 0.11 0.13 0.12 0.12 0.12 0.13 3 0.52 1.7 2.5 3.2 4.0 4.5 5 1.3 2.4 2.6 2.7 2.8 3.0 7 0.67 1.4 1.5 1.4 1.5 1.6 VO(pp) 10.0 10.1 10.2 10.2 10.2 10.2 VO 230 230 230 230 230 230 IO 0.350 0.350 0.350 0.350 0.350 0.350 PO 80.5 80.5 80.5 80.5 80.5 80.5 n(%) 94.0 94.6 94.9 95.3 95.6 95.7 DC Output This data was taken with the test set-up shown in Figure 17. T = Coilcraft N2881-A Primary: 62 turns of # 22 AWG Secondary: 5 turns of # 22 AWG Core: Coilcraft PT2510, EE 25 Gap: 0.072 total for a primary inductance of 320 H Heatsink = AAVID Engineering Inc. 5903B, or 5930B 8 MOTOROLA ANALOG IC DEVICE DATA MC34261 MC33261 Figure 16. 175 W Universal Input Power Factor Controller 1 D2 85 to 265 RFI Vac Filter D4 Zero Current Detector 1.2V + + + 36V 6.7V 5 C6 100k R8 8 + 1N4934 D6 100 C5 22k R5 T D1 D3 1.6V UVLO 2.5V Reference + 10V MUR460 D5 + 7 10 R6 MTW 14N50E Q1 Timer R Delay RS Latch 1.3M R7 16V Drive Output 10 10 VO 400V/0.44A 180 C4 Current Sense Comparator Multiplier 3 6 4 + Error Amp Vref 0.5mA 1 2 0.68 C1 330 R4 1.0nF C3 0.1 R9 1.6M R2 0.01 C2 12k R3 10k R1 Power Factor Controller Test Data AC Line Input Current Harmonic Distortion (%) Vrms 90 120 138 180 240 268 Pin 187.5 184.6 183.6 181.0 179.3 178.6 PF -0.998 -0.997 -0.997 -0.995 -0.993 -0.992 THD 2.0 1.8 2.3 4.3 6.0 6.7 2 0.10 0.09 0.05 0.16 0.08 0.16 3 0.98 1.3 1.6 2.5 3.7 2.8 5 0.90 1.3 1.5 2.0 2.7 3.7 7 0.78 0.93 1.0 1.2 1.4 1.7 VO(pp) 8.0 8.0 8.0 8.0 8.0 8.0 VO 400.7 400.7 400.7 400.6 400.6 400.6 IO 0.436 0.436 0.436 0.436 0.436 0.436 PO 174.7 174.7 174.7 174.7 174.7 174.7 n(%) 93.2 94.6 95.2 95.6 97.4 97.8 DC Output This data was taken with the test set-up shown in Figure 17. T = Coilcraft N2880-A Primary: 78 turns of # 16 AWG Secondary: 6 turns of # 18 AWG Core: Coilcraft PT4215, EE 42-15 Gap: 0.104 total for a primary inductance of 870 H Heatsink = AAVID Engineering Inc. 5903B MOTOROLA ANALOG IC DEVICE DATA 9 MC34261 MC33261 Figure 17. Power Factor Test Set-Up 2X Step-Up Isolation Transformer RFI Filter AC POWER ANALYZER PM 1000 W VA PF Vrms Arms Line 115 Vac Input Neutral HI HI T Autoformer I O A LO LO V 0.1 0.005 1.0 0.005 0 Vcf 7 1 9 2 11 3 13 5 Voltech 0 to 270 Vac Output Power Factor Controller Circuit Acf Ainst FREQ HARM Earth An RFI filter is required for best performance when connecting the preconverter directly to the AC line. Commercially available two stage filters such as the Delta Electronics 03DPCG5 work excellent. The simple single stage test filter shown above can easily be constructed with a common mode transformer. Transformer (T) is a Coilcraft CMT3-28-2 with 28 mH minimum inductance and a 2.0 A maximum current rating. Figure 18. Soft-Start Circuit Figure 19. Error Amp Compensation + 0.5 mA 1 2 To VO 10A Error Amp + 1 R1 6 2 C1 R2 C + 1.0M To VCC tSoft-Start 9000C in F Startup overshoot can be eliminated with the addition of a Soft-Start circuit. 10 MOTOROLA ANALOG IC DEVICE DATA MC34261 MC33261 Figure 20. Printed Circuit Board and Component Layout (Circuits of Figures 15 and 16) MOTOROLA ANALOG IC DEVICE DATA 11 MC34261 MC33261 OUTLINE DIMENSIONS P SUFFIX PLASTIC PACKAGE CASE 626-05 ISSUE K -B- 1 4 8 5 NOTES: 1. DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL. 2. PACKAGE CONTOUR OPTIONAL (ROUND OR SQUARE CORNERS). 3. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. DIM A B C D F G H J K L M N MILLIMETERS MIN MAX 9.40 10.16 6.10 6.60 3.94 4.45 0.38 0.51 1.02 1.78 2.54 BSC 0.76 1.27 0.20 0.30 2.92 3.43 7.62 BSC --- 10_ 0.76 1.01 INCHES MIN MAX 0.370 0.400 0.240 0.260 0.155 0.175 0.015 0.020 0.040 0.070 0.100 BSC 0.030 0.050 0.008 0.012 0.115 0.135 0.300 BSC --- 10_ 0.030 0.040 F NOTE 2 -A- L C -T- SEATING PLANE J N D K M M H G 0.13 (0.005) TA M B M -A- 8 5 D SUFFIX PLASTIC PACKAGE CASE 751-05 (SO-8) ISSUE N -B- 1 4 4X P 0.25 (0.010) M B M NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. MILLIMETERS MIN MAX 4.80 5.00 3.80 4.00 1.35 1.75 0.35 0.49 0.40 1.25 1.27 BSC 0.18 0.25 0.10 0.25 0_ 7_ 5.80 6.20 0.25 0.50 INCHES MIN MAX 0.189 0.196 0.150 0.157 0.054 0.068 0.014 0.019 0.016 0.049 0.050 BSC 0.007 0.009 0.004 0.009 0_ 7_ 0.229 0.244 0.010 0.019 G C -T- 8X SEATING PLANE R X 45 _ F D 0.25 (0.010) M K TB M_ S J S A DIM A B C D F G J K M P R Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. "Typical" parameters which may be provided in Motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. Motorola does not convey any license under its patent rights nor the rights of others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that Motorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal Opportunity/Affirmative Action Employer. Mfax is a trademark of Motorola, Inc. How to reach us: USA / EUROPE / Locations Not Listed: Motorola Literature Distribution; P.O. Box 5405, Denver, Colorado 80217. 303-675-2140 or 1-800-441-2447 JAPAN: Nippon Motorola Ltd.: SPD, Strategic Planning Office, 4-32-1, Nishi-Gotanda, Shinagawa-ku, Tokyo 141, Japan. 81-3-5487-8488 MfaxTM: RMFAX0@email.sps.mot.com - TOUCHTONE 602-244-6609 ASIA/PACIFIC: Motorola Semiconductors H.K. Ltd.; 8B Tai Ping Industrial Park, - US & Canada ONLY 1-800-774-1848 51 Ting Kok Road, Tai Po, N.T., Hong Kong. 852-26629298 INTERNET: http://motorola.com/sps 12 MC34261/D MOTOROLA ANALOG IC DEVICE DATA |
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